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1/16 www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. single-chip type with built-in fet switching regulator series output 1.5a or less high efficiency step-down switching regulator with built-in power mosfet bd9150muv description rohm?s high efficiency dual step-down switching regulator bd 9150muv is a 2ch output power supply designed to produce a low voltage including 3.3,1.2 volts from 5. 0 volts power supply line. offers high efficiency with our original pulse skip con trol technology and synchronous rectifier. employs a current mode co ntrol system to provide faster transient response to sudden change in load. features 1) offers fast transient response with current mode pwm control system. 2) offers highly efficiency for all load range with synchronous rectifier (pch/nch fet) and sllm tm (simple light load mode) 3) 2ch output power supply. 4) each of en controls 2ch output. 5) incorporates soft-start function. 6) incorporates ulvo functions. 7) incorporates thermal protection and short-curr ent protection circuit with time delay function. 8) incorporates shutdown function icc=0 a(typ.) 9) output current max 1.5a/1.5a. 10) employs small surface mount package : vqfn020v4040 use power supply for lsi including dsp, micro computer and asic absolute maximu m rating (ta=25 ) parameter symbol limit unit vcc voltage v cc -0.3 +7 * 1 v en voltage v en1 -0.3 +7 v v en2 -0.3 +7 v sw voltage v sw1 -0.3 +7 v v sw2 -0.3 +7 v power dissipation pd1 0.34* 2 w pd2 0.70 * 3 w pd3 1.21 * 4 w pd4 3.56* 5 w operating temperature range topr -40 +85 storage temperature range tstg -55 +150 maximum junction tjmax +150 *1 pd should not be exceeded. *2 ic only *3 1-layer. mounted on a 74.2mm 74.2mm 1.6mm glass-epoxy board, occupied area by copper foil : 10.29mm 2 *4 4-layer. mounted on a 74.2mm 74.2mm 1.6mm glass-epoxy board, occupied area by copper foil : 10.29mm 2 , in each layers *5 4-layer. mounted on a 74.2mm 74.2mm 1.6mm glass-epoxy board, occupied area by copper foil : 5505mm 2 , in each layers no.10027ect13
technical note 2/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. operating conditions (ta=-40 +85 ) parameter symbol limit unit min. typ. max. vcc voltage v cc 4.75 5.0 5.5 v en voltage v en 1 0 - 5.5 v v en 2 0 - 5.5 v output voltage range v out 2 0.8 - 2.5 v sw average output current i sw 1 - - 1.5* 6 a i sw 2 - - 1.5* 6 a *6 pd and aso should not be exceeded. electrical characteristics (ta=25 av cc =pv cc =5.0v, en1=en2=av cc ,unless otherwise specified.) parameter symbol limit unit condition min. typ. max. standby current i stb - 0 10 a en1=en2=0v bias current i cc - 500 800 a en low voltage v enl - gnd 0.8 v standby mode en high voltage v enh 2.0 vcc - v active mode en input current i en - 1 10 a ven1=ven2=2v oscillation frequency f osc 1.2 1.5 1.8 mhz pch fet on resistance r onp 1 - 0.17 0.3 ? vcc=5v r onp 2 - 0.17 0.3 ? vcc=5v nch fet on resistance r onn 1 - 0.13 0.2 ? vcc=5v r onn 2 - 0.13 0.2 ? vcc=5v fb reference voltage fb1 3.25 3.3 3.35 v 1.5% fb2 0.788 0.8 0.812 v 1.5% uvlo threshold voltage v uvlo 1 3.6 3.8 4.0 v v cc =5 0v uvlo release voltage v uvlo 2 3.65 3.9 4.2 v v cc =0 5v soft start time t ss 0.4 0.8 1.6 ms timer latch time t latch 0.68 1.36 2.72 ms scp/tsd on output short circuit threshold voltage v scp 1 - 1.65 2.4 v fb1=3.3 0v v scp 2 - 0.4 0.56 v fb2=0.8 0v
technical note 3/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. block diagram, application circuit bd9150muv fig.1 bd9150muv top view fig.2 bd9150muv block diagram pin no. & function table pin no. pin name function pin no. pin name function 1 pgnd2 ch2 lowside source pin 11 ith1 ch1 gmamp output pin/connected phase compensation capacitor 2 pvcc highside fet source pin 12 agnd ground 3 pvcc highside fet source pin 13 n.c. non connection 4 pvcc highside fet source pin 14 avcc vcc power supply input pin 5 pgnd1 ch1 lowside source pin 15 ith2 ch1 gmamp output pin/connected phase compensation capacitor 6 pgnd1 ch1 lowside source pin 16 fb2 ch2 output voltage detect pin 7 sw1 ch1 pch/nch fet drain output pin 17 en2 ch2 enable pin(high active 8 sw1 ch1 pch/nch fet drain output pin 18 sw2 ch2 pch/nch fet drain output pin 9 en1 ch1 enable pin(high active) 19 sw2 ch2 pch/nch fet drain output pin 10 fb1 ch1 output voltage detect pin 20 pgnd2 ch2 lowside source pin (unit : mm) 2.1 0.1 c0.2 0.5 1.0 15 6 10 11 15 16 20 4.0 0.1 4.0 0.1 2.1 0.1 0.4 0.1 0.25 +0.05 -0.04 0.02 +0.03 -0.02 1.0max. (0.22) 0.08 s s d9150 lot no. current sense/ protect + driver logic soft start1 slope1 r s q osc vref scp/ tsd scp2 current sense/ protect + driver logic soft start2 slope2 r s q scp1 clk2 gm amp current comp gm amp current comp clk1 clk2 uvlo fb1 en1 fb2 en2 pv cc sw1 pgnd2 sw2 agnd ith1 ith2 a gnd a v cc pv cc pgnd1
technical note 4/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 012345 input voltage:v cc [v] output voltage:vout[v] characteristics data fig.3 vcc - v out fig.4 v en - v out fig.5 i out - v out fig. 6 ta - vout fig. 7 ta - v out fig.8 efficiency fig.9 ta - fosc fig.10 vcc - fosc fig.11 ta ? r onn , r onp fig.12 ta-v en fig.13 ta-i cc fig.14 soft start waveform (io=0ma) 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 01234 output current:i out [a] output voltage:vout[v] 1.3 1.4 1.5 1.6 1.7 4.5 4.75 5 5.25 5.5 input voltage:v cc [v] frequency:f osc [mhz] 1.3 1.4 1.5 1.6 1.7 -40-200 20406080 temperature:ta[ ] frequency:fosc[mhz] 0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 -40-20 0 20406080 temperature:ta[ ] en voltage:ven[v] 0 25 50 75 100 125 150 175 200 -40 -20 0 20 40 60 80 100 temperature:ta[ ] on resistance:r on [m ] vout2=1.2v ta = 2 5 io=1.5a 3.20 3.25 3.30 3.35 3.40 -40 -20 0 20 40 60 80 temperature:ta[ ] output voltage:vout[v] vcc=5v io=0a vout1=3.3v vcc=5v 0 100 200 300 400 500 600 -40-20 0 20406080 temperature:ta[ ] circuit current:i cc [ a] vcc=5v vout1=3.3v 0 10 20 30 40 50 60 70 80 90 100 10 100 1000 10000 output current:i out [ma] efficiency: [%] vcc=5v ta = 2 5 vout2=2.5v vout2=1.5v vout2=1.2v ta = 2 5 pmos nmos vcc=5v vout2=1.2v vcc=5v ta = 2 5 vout1=3.3v 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 012345 en voltage:ven[v] output voltage:vout[v] vcc=5v ta = 2 5 io=0a vout2=1.2v vout1=3.3v vout1=3.3v vout2=1.2v O 1.15 1.18 1.20 1.23 1.25 -40-200 2040 6080 tem perature:ta[ ] output voltage:vout[v] vout2=1.2v vcc=5v io=0a vcc=5v en1=e2 vout1 vout2 vcc=5v,ta=25
technical note 5/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. characteristics data bd9150muv fig.15 soft start waveform (io=1.5a) fig.16 sw1 waveform (io=0ma) fig.17 sw1 waveform (io=1.5a) fig.18 sw2 waveform (io=0ma) fig.19 sw2 waveform (io=1.5a) fig.20 vout1 transient response (io0.5a 1.5a / usec) fig.21vout1 transient response (io1.5a 0.5a/ usec) fig.22 vout2 transient response (io0.5a 1.5a/ usec) fig.23 vout2 transient response (io1.5a 0.5a/ usec) vcc=5v,ta=25 vcc=5v,ta=25 vcc=5v,ta=25 ,vout2=1.2v vcc=5v,ta=25 ,vout2=1.2v vcc=5v,ta=25 ,vout2=1.2v vcc=5v,ta=25 ,vout2=1.2v vcc=5v,ta=25 vcc=5v,ta=25 en1=e2 vout1 vout2 vout1 sw1 vout1 sw1 vout2 sw2 vout2 sw2 iout1 vout1 iout1 vout1 iout2 vout2 iout2 vout2 vcc=5v,ta=25
technical note 6/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. information on advantages advantage 1 offers fast transient response with current mode control system. fig.24transient response advantage 2 offers high efficiency for all load range. ? for lighter load: utilizes the current mode control mode called sllm for lighter load, which reduces various dissipation such as switching dissipation (p sw ), gate charge/discharge dissipation, esr dissipation of output capacitor (p esr ) and on-resistance dissipation (p ron ) that may otherwise cause degradation in efficiency for lighter load. achieves efficiency improvement for lighter load. ? for heavier load: utilizes the synchronous rectifying mode and the low on-re sistance mos fets incorporated as power transistor. on resistance of highside mos fet : 170m (typ.) on resistance of lowside mos fet : 130m (typ.) achieves efficiency improvement for heavier load. offers high efficiency for all load rang e with the improvements mentioned above. advantage 3 ? supplied in smaller package due to small-sized power mos fet incorporated. reduces a mounting area required. fig.26 example application fig.25 efficiency bd9150muv (load response i o =0.5a 1.5a) bd9150muv (load response i o =1.5a 0.5a) ? output capacitor co required for current mode control: 22 f ceramic capacitor ? inductance l required for the oper ating frequency of 1 mhz: 2.2 h inductor ? incorporates fet + boot strap diode 0.001 0.01 0.1 1 0 50 100 pwm sllm inprovement by sllm system improvement by synchronous rectifier efficiency [%] output current io[a] v out i out v out i out l1 vout1 ith1 fb1 en1 sw1 sw1 agnd pgnd1 pvcc cout1 cin1 pgnd1 rith1 l2 fb2 en2 sw2 sw2 n.c . avcc ith2 pvcc pvc c pgnd2 vout2 r2 r1 cin2 cout2 pgnd2 rith2 cith2 cith 1 15mm 20mm cith1 l1 r1 rith1 cin1 cin2 cout1 cout2 l2 r2 cith2 rith2
technical note 7/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. operation bd9150muv is a synchronous rectifying step-down switching regu lator that achieves faster transient response by employing current mode pwm control system. it utiliz es switching operation in pwm (pulse width modulation) mode for heavier load, while it utilizes sllm (simple light load mode) oper ation for lighter load to improve efficiency. synchronous rectifier it does not require the power to be dissipated by a rectifier exte rnally connected to a conventional dc/dc converter ic, and it s p.n junction shoot-through protection circui t limits the shoot-through current during o peration, by which the power dissipation of the set is reduced. current mode pwm control synthesizes a pwm control signal with a inductor current feedback loop added to the voltage feedback. ? pwm (pulse width modulation) control the oscillation frequency for pwm is 1 mhz. set signal fo rm osc turns on a highside mos fet (while a lowside mos fet is turned off), and an inductor current i l increases. the current comparator (c urrent comp) receives two signals, a current feedback control signal ( sense: voltage converted from i l ) and a voltage feedback control signal (fb), and issues a reset signal if both input signals are identical to each ot her, and turns off the highside mos fet (while a lowside mos fet is turned on) for the rest of the fixed period . the pwm control repeat this operation. ? sllm (simple light load mode) control when the control mode is shifted from pwm for heavier load to the one for lighter load or vise versa, the switching pulse is designed to turn off with the device held operated in norma l pwm control loop, which allows linear operation without voltage drop or deterioration in transient response during the mo de switching from light load to heavy load or vise versa. although the pwm control loop continues to operate with a set signal from osc and a reset signal from current comp, it is so designed that the rese t signal is held issued if shifted to the light load mode, with which the switching is tuned off and the switching pulses are thinned out u nder control. activating the switching intermittently reduces the switching dissipation and improves the efficiency. fig.27 diagram of current mode pwm control osc level shift driver logic rq s i l sw ith current comp gm amp. set reset fb load sense v out v out fi g. 28 pwm sw i tc hi ng t i m i ng c h art fig.29 sllm tm switching timing chart curren t comp set reset sw v out pvcc gnd gnd gnd i l (ave) v out (ave) sense fb curren t comp set reset sw v out pvcc gnd gnd gnd 0a v out (ave) sense fb i l not switching i l
technical note 8/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. description of operations ? soft-start function en terminal shifted to ?high? activates a soft-starter to gr adually establish the output voltag e with the current limited durin g startup, by which it is possible to prevent an ov ershoot of output voltage and an inrush current. ? shutdown function with en terminal shifted to ?low?, the device turns to standby mode, and all the function blocks including reference voltage circuit, internal oscillator and drivers are turn ed to off. circuit current during standby is 0 f (typ.). ? uvlo function detects whether the input voltage sufficient to secure the output voltage of this ic is supplied. and the hysteresis width of 100mv (typ.) is provided to prevent output chattering. fig.30 soft start, shutdown, uvlo timing chart ? short-current protection circuit with time delay function turns off the output to protect the ic fr om breakdown when the incorporated current limiter is activated continuously for the fixed time(t latch ) or more. the output thus held tuned off may be recovered by restarting en or by re-unlocking uvlo. fig.31 short-current protection circuit with time delay timing chart hysteresis 100mv ts s ts s ts s soft start standby mode operating mode standby mode operating mode standby mode operating mode standby mode uvlo en uvlo uvlo v cc en1,en2 v out1, v out2 output short circuit threshold voltage i l limi t en timer latch en standby mode operating mode operating mode standby mode en1 en2 t2=t latch v out2 i l1 t1 technical note 9/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. switching regulator efficiency efficiency ? may be expressed by the equation shown below: efficiency may be improved by reducing the swit ching regulator power dissipation factors p d as follows: dissipation factors: 1) on resistance dissipation of inductor and fet pd(i 2 r) 2) gate charge/discharge dissipation pd(gate) 3) switching dissipation pd(sw) 4) esr dissipation of capacitor pd(esr) 5) operating current dissipation of ic pd(ic) 1)pd(i 2 r)=i out 2 (r coil +r on ) (r coil [ ] dc resistance of inductor, r on [ ] on resistance of fet, i out [a] output current.) 2)pd(gate)=cgs f v (cgs[f] gate capacitance of fet, f[h] switching frequency, v[v] gate driving voltage of fet) 4)pd(esr)=i rms 2 esr (i rms [a] ripple current of capacitor, esr[ ] equivalent series resistance.) 5)pd(ic)=vin i cc (i cc [a] circuit current.) = v out i out vin iin 100[%]= p out pin 100[%]= p out p out +p d 100[%] vin 2 c rss i out f i drive 3)pd(sw)= (c rss [f] reverse transfer capacitance of fet, i drive [a] peak current of gate.)
technical note 10/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. consideration on permissible dissipation and heat generation as this ic functions with high efficien cy without significant heat generation in most applications, no special consideration is needed on permissible dissipation or heat generation. in case of extreme conditions, however, including lower input voltage, higher output voltage, heavier load, and/or higher temperature, the permissible di ssipation and/or heat generation must be carefully considered. for dissipation, only conduction losses due to dc resistance of inductor and on resistance of fet are considered. because the conduction losses are considered to play the leading role among other dissipation mentioned above including gate charge/discharge dissipation and switching dissipation. p=i out 2 r on r on =d r onp +(1-d)r onn d on duty (=v out /v cc ) r onh on resistance of highside mos fet r onl on resistance of lowside mos fet i out output current if v cc =5v, v out1 =3.3v, v out2 =1.2v, r onh =170m , r onl =130m i out =1.5a, for example, d 1 =v out1 /v cc =3.3/5=0.66 d 2 =v out2 /v cc =1.2/5=0.24 r on1 =0.66 0.170+(1-0.66) 0.130 =0.1122+0.0442 =0.1564[ ] r on2 =0.24 0.170+(1-0.24) 0.130 =0.0408+0.0988 =0.1397[ ] p=1.5 2 0.1564+1.5 2 0.1397=0.666[w] as r onh is greater than r onl in this ic, the dissipation increases as the on duty becomes greater. with the consideration on the dissipation as above, thermal design must be carried out with sufficient margin allowed. fig.32 thermal derating curve (vqfn020v4040) power dissipation:pd [w] ambient temperature:ta [ ] 0 2.0 3.0 4.0 1.21w 3.56w 1.0 4.5 0.70w 0.34w 4 layers (copper foil area : 5505mm 2 ) (copper foil in each layers) j-a=32.1 /w 4 layers (copper foil area : 10.29mm 2 ) (copper foil in each layers) j-a=82.6 /w 1 layer (copper foil area : 0mm 2 ) j-a=160.1 /w ic only j-a=249.5 /w 0 25 50 75 100 125 150 105
technical note 11/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. selection of components externally connected 1. selection of inductor (l) current exceeding the current rating of the inductor results in magnetic saturation of the inductor, which decreases efficiency . the inductor must be selected allowing sufficient margin with which the peak current may not exceed its current rating. if v cc =5.0v, v out =1.2v, f=1.5mhz, i l =0.2 1.5a=0.3a, for example,(bd9150muv) select the inductor of low resistance component (such as dcr an d acr) to minimize dissipati on in the inductor for better efficiency. 2. selection of output capacitor (c o ) 3. selection of input capacitor (cin) a low esr 22 f/10v ceramic capacitor is recommended to reduce esr dissipation of input capacitor for better efficiency. the inductance significantly depe nds on output ripple current. a s seen in the equation (1), the ripple current decreases as the inductor and/or switching frequency increases. i l = (v cc -v out ) v out l v cc f [ a ] ??? ( 1 ) a ppropriate ripple current at output should be 20% more or less of the maximum out p ut current. i l =0.2 i out max. [a] ??? (2) l= (v cc -v out ) v out i l v cc f [ h ] ??? ( 3 ) ( i l : output ripple current, and f: switching frequency) output capacitor should be selected with the consideration on the stability region and the equivalent series resistance re quired to smooth ripple voltage. output ripple voltage is determined by the equation (4) v out = i l esr [v] ??? (4) ( i l : output ripple current, esr: equivalent series resistance of output capacitor) rating of the capacitor should be determined allowing sufficient margin against output voltage. a 22 f to 100 f ceramic capacitor is recommended. less esr allows reduction in output ripple voltage. input capacitor to select must be a low esr capacitor of the capacitance sufficient to cope with high ripple current to prevent high transient voltage. the ripple current irms is given by the equation (5): i rms =i out v out ( v cc -v out ) v cc [ a ] ??? ( 5 ) when vcc=2 v out , i rms = i out 2 fig.34 output capacitor ( 5-1.2 ) 1.2 0.3 5 1.5m l= =2.02 2.2[ h] < worst case > i rms(max.) i rms =2 1.2 ( 5.0-1.2 ) 5.0 =0.85[a rms ] fig.35 input capacitor i l v out fig.33 output ripple current i l v cc il l co v cc l co v out esr v out v cc l co cin if v cc =5.0v, v out =1.2v, and i outmax.= 1.5a, (bd9150muv)
technical note 12/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. 4. determination of rith, cith that works as a phase compensator as the current mode control is designed to limit a inductor current, a pole (phase lag) appears in the low frequency area due to a cr filter consisting of a output capacitor and a load resistance, while a zero (phase lead) appears in the high frequency area due to the output capacitor and its esr. so, the phases are easily compensated by adding a zero to the power amplifier output with c and r as described bel ow to cancel a pole at the power amplifier. stable feedback loop may be achieved by canceling the pole fp (min.) produced by the output capacitor and the load resistance with cr zero correction by the error amplifier. gain [db] phase [deg] fig.36 open loop gain characteristics a 0 0 -90 a 0 0 -90 fz(amp.) fig.37 error amp phase compensation characteristics fp= 2 r o c o 1 fz (esr) = 2 e sr c o 1 pole at power amplifie r when the output current decreases, the load resistance ro increases and the pole frequency lowers. fp (min.) = 2 r omax. c o 1 [hz] with lighter load fp (max.) = 2 r omin. c o 1 [hz] with heavier load zero at power amplifie r fz (amp.) = 2 r ith c ith 1 fig.38 typical application fz (amp.) = fp (min.) 2 r ith c ith 1 = 2 r omax. c o 1 fp(min.) fp(max.) fz(esr) i out min. i out max. gain [db] phase [deg] increasing capacitance of the out put capacitor lowers the pole frequency while the zero frequency does not change. (this is because when the capacitance is doubled, the capacitor esr reduces to half.) l1 vout1 ith1 fb1 en1 sw1 sw1 agnd pgnd1 pvc c cout1 cin1 pgnd1 rith1 l2 fb2 en2 sw2 sw2 n.c . avcc ith2 pvc c pvc c pgnd2 vout2 r2 r1 cin2 cout2 pgnd2 rith2 cith2 cith 1 ro2 ro1 esr esr
technical note 13/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. 5. determination of output voltage the output voltage vout is determined by the equation (6): vout=(r2/r1+1) vadj ??? (6) vadj: voltage at adj terminal (0.8v typ.) with r1 and r2 adjusted, the output vo ltage may be determined as required. adjustable output voltage range : 0.8v 2.5v fig.39 determination of output voltage use 1 k ? 100 k ? resistor for r1. if a resistor of the resistance higher than 100 k ? is used, check the assembled set carefully for ripple voltage etc. bd9150muv cautions on pc board layout fig.40 layout diagram lay out the input ceramic capacitor cin closer to the pins pvcc and pgnd, and the output capacitor co closer to the pin pgnd. lay out cith and rith between the pi ns ith and gnd as neat as possible with least necessary wiring. vqfn020v4040 (bd9150muv) has thermal pad on the reverse of the package. the package thermal performance may be enhanced by bonding t he pad to gnd plane which take a large area of pcb. sw2 fb2 l2 cout2 r2 r1 output l2 l1 v out1 ith1 fb1 en1 sw1 sw1 fb2 en2 sw2 sw2 agnd n.c. avcc ith2 pgnd1 pvc c pvc c pvc c pgnd2 v out2 c out 1 c in 1 r2 r 1 c in 2 c out 2 pgnd2 r ith2 c ith2 pgnd1 r ith1 c ith1
technical note 14/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. recommended components lists on above application symbol part value manufacturer series l1,2 coil 2.2uh tdk ltf5022-2r2n3r2 2.2uh tdk ltf5022-2r2n3r2 c in1, c in2 ceramic capacitor 22uf murata grm32eb11a226ke20 c out1, c out2 ceramic capacitor 22uf murata grm31cb30j226ke18 c ith1 ceramic capacitor 330pf murata crm18 serise r ith1 resistance 56k rohm mcr03 serise c ith2 ceramic capacitor v out =1.0v 330pf murata crm18 serise v out =1.2v 330pf murata grm18 serise v out =1.5v 330pf murata grm18 serise v out =1.8v 330pf murata grm18 serise v out =2.5v 330pf murata grm18 serise r ith2 resistance v out =1.0v 39k rohm mcr03 serise v out =1.2v 47k rohm mcr03 serise v out =1.5v 56k rohm mcr03 serise v out =1.8v 75k rohm mcr03 serise v out =2.5v 91k rohm mcr03 serise the parts list presented above is an example of recommende d parts. although the parts are sound, actual circuit characteristics should be checked on your application carefu lly before use. be sure to allow sufficient margins to accommodate variations between external devices and this ic when employing the depicted circuit with other circuit constants modified. both static and transient characteristics should be considered in establishing these margins. when switching noise is substantial and may im pact the system, a low pass filter should be inserted between the vcc and pvcc pins, and a schottky barrier diode or snubber established between the sw and pgnd pins. i/o equivalence circuit bd9150muv fig.41 i/o equivalence circuit en1,en2 ? en1,en2 pin ? sw1,sw2 pv cc sw1,sw2 pv cc pv cc ith1,ith2 ? ith1,ith2 pin a v cc ? fb1,fb2 pin fb1,fb2
technical note 15/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. notes for use 1. absolute ma ximum ratings while utmost care is taken to quality control of this pr oduct, any application that may exceed some of the absolute maximum ratings including the voltage applied and the operat ing temperature range may result in breakage. if broken, short-mode or open-mode may not be identif ied. so if it is expected to encounter with special mode that may exceed the absolute maximum ratings, it is requested to take necessary sa fety measures physically including insertion of fuses. 2. electrical potential at gnd gnd must be designed to have the lowest elec trical potential in any operating conditions. 3. short-circuiting between terminals, and mismounting when mounting to pc board, care must be taken to avoid mistak e in its orientation and alignment. failure to do so may result in ic breakdown. short-circuiting due to forei gn matters entered between output terminals, or between output and power supply or gnd may also cause breakdown. 4. thermal shutdown protection circuit thermal shutdown protection circuit is the circuit designed to isolate the ic from thermal runaway, and not intended to protect and guarantee the ic. so, the ic the thermal shutdown protection circui t of which is once activated should not be used thereafter for any operation originally intended. 5. inspection with the ic set to a pc board if a capacitor must be connected to the pin of lower impeda nce during inspection with the ic set to a pc board, the capacitor must be discharged after each process to avoid stress to the ic. for electrostatic protection, provide proper grounding to assembling processes with special care taken in handling and storage. when connecting to jigs in the inspection process, be sure to turn off the power supply before it is connected and removed. 6. input to ic terminals this is a monolithic ic with p + isolation between p-substrate and each element as illustrated below. this p-layer and the n-layer of each element form a p-n junction, and various parasitic element are formed. if a resistor is joined to a transistor terminal as shown in fig 42. p-n junction works as a parasitic diode if the following rela tionship is satisfied; gnd>terminal a (at resistor side), or gnd>terminal b (at transistor side); and if gnd>terminal b (at npn transistor side), a parasitic npn transistor is activated by n-layer of ot her element adjacent to the above-mentioned parasitic diode. the structure of the ic inevitably forms parasitic elements, the activation of which may cause interference among circuits, and/or malfunctions contributing to breakdown . it is therefore requested to take care not to use the device in such manner that the voltage lowe r than gnd (at p-substrate) may be applied to the input terminal, which may result in activation of parasitic elements. fig.42 simplified struct ure of monorisic ic 7. ground wiring pattern if small-signal gnd and large-current gnd are provided, it will be recommended to separate the large-current gnd pattern from the small-signal gnd pattern and establish a si ngle ground at the reference poi nt of the set pcb so that resistance to the wiring pattern and voltage fluctuations due to a large current will cause no fluctuations in voltages of the small-signal gnd. pay attention not to cause fluctuations in the gnd wiring pattern of external parts as well. 8 . selection of inductor it is recommended to use an inductor with a series resistance element (dcr) 0.1 or less. especially, in case output voltage is set 1.6v or more, note that use of a high dcr i nductor will cause an inductor loss , resulting in decreased output voltage. should this condition continue for a specified peri od (soft start time + timer la tch time), output short circuit protection will be activated and output will be latched off. when using an inductor over 0.1 , be careful to ensure adequate margins for variation between external devices and this ic, including transient as well as static characteristics. furthermore, in any case, it is recommended to start up the out put with en after supply voltage is within operation range. resistor transistor (npn) n n n p + p + p p substrate gnd parasitic element pin a n n p + p + p p substrate gnd parasitic element pin b c b e n gnd pin a p aras iti c element pin b other adjacent elements e b c gnd p aras iti c element
technical note 16/16 bd9150muv www.rohm.com 2010.04 - rev.c c 2010 rohm co., ltd. all rights reserved. ordering part number b d 9 1 5 0 m u v - e 2 part no. part no. package muv: vqfn020v4040 packaging and forming specification e2: embossed tape and reel ? order quantity needs to be multiple of the minimum quantity. embossed carrier tape tape quantity direction of feed the direction is the 1pin of product is at the upper left when you hold reel on the left hand and you pull out the tape on the right hand 2500pcs e2 () direction of feed reel 1pin (unit : mm) vqfn020v4040 2.1 0.1 1 15 11 20 16 5 10 6 0.5 1.0 0.25 +0.05 - 0.04 2.1 0.1 0.4 0.1 c0.2 1.0max 0.02 +0.03 - 0.02 (0.22) 4.0 0.1 4.0 0.1 1pin mark 0.08 s s
r1010 a www.rohm.com ? 2010 rohm co., ltd. all rights reserved. notice rohm customer support system http://www.rohm.com/contact/ thank you for your accessing to rohm product informations. more detail product informations and catalogs are available, please contact us. notes no copying or reproduction of this document, in part or in whole, is permitted without the consent of rohm co.,ltd. the content specied herein is subject to change for improvement without notice. the content specied herein is for the purpose of introducing rohm's products (hereinafter "products"). if you wish to use any such product, please be sure to refer to the specications, which can be obtained from rohm upon request. examples of application circuits, circuit constants and any other information contained herein illustrate the standard usage and operations of the products. the peripheral conditions must be taken into account when designing circuits for mass production. great care was taken in ensuring the accuracy of the information specied in this document. however, should you incur any damage arising from any inaccuracy or misprint of such information, rohm shall bear no responsibility for such damage. the technical information specied herein is intended only to show the typical functions of and examples of application circuits for the products. rohm does not grant you, explicitly or implicitly, any license to use or exercise intellectual property or other rights held by rohm and other parties. rohm shall bear no responsibility whatsoever for any dispute arising from the use of such technical information. the products specied in this document are intended to be used with general-use electronic equipment or devices (such as audio visual equipment, ofce-automation equipment, commu- nication devices, electronic appliances and amusement devices). the products specied in this document are not designed to be radiation tolerant. while rohm always makes efforts to enhance the quality and reliability of its products, a product may fail or malfunction for a variety of reasons. please be sure to implement in your equipment using the products safety measures to guard against the possibility of physical injury, re or any other damage caused in the event of the failure of any product, such as derating, redunda ncy, re control and fail-safe designs. rohm shall bear no responsibility whatsoever for your use of any product outside of the prescribed scope or not in accordance with the instruction manual. the products are not designed or manufactured to be used with any equipment, device or system which requires an extremely high level of reliability the failure or malfunction of which may result in a direct threat to human life or create a risk of human injury (such as a medical instrument, transportation equipment, aerospac e machinery, nuclear-reactor controller, fuel- controller or other safety device). rohm shall bear no responsibility in any way for use of any of the products for the above special purposes. if a product is intended to be used for any such special purpose, please contact a rohm sales representative before purchasing. if you intend to export or ship overseas any product or technology specied herein that may be controlled under the foreign exchange and the foreign trade law, you will be required to obtain a license or permit under the law.

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